• 专利附录
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    • 专利摘要:
    PURPOSE: A method and an apparatus for compensating the frequency offset for interleaved FDMA(Frequency Division Multiple Access) are provided to reduce the cost of the circuit design and implementation as well as to compensate the frequency offset before the channel characteristics is estimated. CONSTITUTION: A method for compensating the frequency offset for interleaved FDMA includes: a step of estimating the frequency offset for the u-th user(10); a step of estimating the interference amount of the reception signal for the u-th user(12); a step of calculating the feedback signal by subtracting the interference amount from the reception signal(14); a step of determining whether the above steps are repeated by a predetermined times or not(16); and a step of estimating the transmission signal by using the feedback signal and the frequency offset when the determined result at the step(16) is affirmative(18).
    公开号:KR20040011645A
    申请号:KR1020020044461
    申请日:2002-07-27
    公开日:2004-02-11
    发明作者:김영수；황찬수
    申请人:삼성전자주식회사；
    IPC主号:
    专利说明:

    Method and apparatus for compensating frequency offset for interleaved frequency division multiple access {method and apparatus for compensating for the frequency offset in interleaved frequency division multiple access}
    [15] The present invention relates to frequency division multiple access (FDMA), and more particularly to a method and apparatus for compensating frequency offset in interleaved frequency division multiple access (IFDMA).
    [16] In an IFDMA communication device using interleaved frequency division multiple access, the frequency offset not only changes the magnitude and phase of the signal transmitted from the transmitter to the receiver, but also causes interference between users, resulting in a received signal-to-noise ratio (SNR). Lowers. Here, IFDMA is a method of implementing multiple carriers in the time domain, and the journal "Interleaved FDMA-A new spread spectrum multiple access scheme" was published in 1998 by Uli sorger, Isabella de Broeck and Michael Schnell in ICC. Proc), pages 1013-1017. At this time, the frequency offset is caused by the difference between the oscillation frequencies generated in the transmission oscillator (not shown) of the transmitter of the IFDMA communication device and the reception oscillator (not shown) of the receiver. To address this, that is, to minimize the frequency offset, very precise analog radio radio (RF) / intermediate frequency (IF) components must be used in the transmitter and receiver of the IFDMA communication device. However, as the frequency offset increases, it is difficult to implement an analog RF / IF component that satisfies the desired performance, and even if the component is implemented, there is a problem that the manufacturing cost of the analog RF / IF component increases.
    [17] An object of the present invention is to provide a frequency offset compensation method for interleaved frequency division multiple access that can compensate for the effects of the existing frequency offset instead of removing the frequency offset without using the channel characteristics. There is.
    [18] Another object of the present invention is to provide a frequency offset compensation device for an interleaved frequency division multiple access for performing the frequency offset compensation method for the interleaved frequency division multiple access.
    [1] 1 is a flowchart illustrating a frequency offset compensation method for IFDMA according to the present invention.
    [2] 2 is a block diagram of an IFDMA communication device having a frequency offset compensation device according to the present invention.
    [3] 3 is a block diagram of a frequency offset compensation device according to the present invention.
    [4] 4 is a block diagram of a preferred embodiment of the present invention of the main frequency offset estimator shown in FIG.
    [5] 5 is a block diagram of a preferred embodiment of the present invention of the transmission signal estimator shown in FIG. 3.
    [6] FIG. 6 is a block diagram of a preferred embodiment of the present invention of the interference amount estimator shown in FIG. 3.
    [7] FIG. 7 is a block diagram of a preferred embodiment of the present invention of an i-th type frequency offset estimator shown in FIG. 6.
    [8] FIG. 8 is a block diagram of a preferred embodiment of the present invention of the ith degree estimator shown in FIG. 6.
    [9] 9 is a block diagram of a preferred embodiment of the present invention of the feedback signal generator shown in FIG. 6.
    [10] 10 is a diagram showing the constellation of an ideal received signal having no frequency offset.
    [11] FIG. 11 is a diagram illustrating a property of a received signal when the frequency offset is 3% of the interval between subcarriers.
    [12] FIG. 12 is a diagram illustrating a constellation of a received signal that can be seen when applying the frequency offset compensation method and apparatus according to the present invention to the constellation shown in FIG. 11.
    [13] 13 is a graph illustrating a change in SNR according to a frequency offset.
    [14] 14 is a graph illustrating a change in BER according to a frequency offset.
    [19] In order to achieve the above object, in the interleaved frequency division multiple access (IFDMA), compensate for the frequency offset between the transmission signal and the reception signal for u (1 ≦ u ≦ U), where U represents the number of users. The frequency offset compensation method according to the present invention comprises the steps of (a) estimating the frequency offset from the selection signal determined as the received signal in the initial state and the feedback signal in the normal state, and the (B) estimating an interference amount representing an interference degree of the received signals with respect to the i (1 ≦ i ≦ U-1) th other users, subtracting the estimated interference amount from the received signal, and (C) determining the subtracted result as the feedback signal, and determining whether the steps (a), (b), and (c) have been repeatedly performed a predetermined number of times; If it is determined that steps (b) and (c) have not been repeatedly performed the predetermined number of times, step (d) and steps (a), (b) and (c) proceed to step (a). If it is determined that they have been repeatedly performed the predetermined number of times, it is preferable that the step (e) of estimating the transmission signal using the feedback signal and the estimated frequency offset finally determined in the step (c).
    [20] In order to achieve the above another object, in the interleaved frequency division multiple access (IFDMA) u (1 ≦ u ≦ U), where U represents the number of users. A frequency offset compensation device according to the present invention for compensating determines the received signal or feedback signal as a selection signal in response to a first control signal, estimates the frequency offset from the selection signal, and outputs the estimated frequency offset. A main frequency offset estimator and an amount of interference representing the degree to which the received signals for the i (1 ≦ i ≦ U-1) th users interfere with the received signal for the uth user. An estimate of the interference from the received signals, the selection signal, and the estimated frequency offset for the signal, and output the estimated amount of interference And a subtraction unit for subtracting the estimated interference amount from the received signal and outputting the subtracted result as the feedback signal, and receiving the first control signal in response to a result of analyzing a state of the frequency offset offset compensator. A control unit for checking whether a predetermined period has elapsed and outputting a second control signal in response to the checked result, and the feedback signal finally inputted from the subtraction unit in response to the second control signal and the estimated A transmission signal estimator for estimating the transmission signal from a frequency offset and outputting the estimated transmission signal, and in response to the second control signal, the main frequency offset estimator, the interference amount estimator, and the subtractor; It is preferable to enable.
    [21] Hereinafter, a frequency offset compensation method for interleaved frequency division multiple access (IFDMA) according to the present invention will be described with reference to the accompanying drawings.
    [22] 1 is a flowchart illustrating a frequency offset compensation method for IFDMA according to the present invention, comprising: estimating a frequency offset and an interference amount (10th and 12th steps), and obtaining a feedback signal (14th step) And estimating the transmission signal (16th and 18th steps).
    [23] The frequency offset compensation method according to the present invention shown in Fig. 1 shows a frequency offset between a transmission signal and a reception signal for the u-th (where u represents the number of users) in the IFDMA communication. Estimate the transmitted signal from the received signal while compensating. Here, a frequency offset is caused by an error between the transmit oscillator (not shown) used in the transmitter to generate the transmitted signal and the receive oscillator (not shown) used in the receiver to generate the received signal.
    [24] In the frequency offset compensation method according to the present invention, first, the frequency offset for the u-th user from the selection signal ( ) Is estimated (step 10). Here, the reception signal is determined as the selection signal in the initial state where the frequency offset compensation method according to the present invention starts to be performed, and the feedback signal is determined as the selection signal in the normal state after the initial state has elapsed. The frequency offset from the selection signal determined in this way ( ) Can be estimated as in Equation 1 below.
    [25]
    [26] here, , C u is a correlation value (Correlation) as shown in the following equation (2).
    [27]
    [28] Here, N u represents the number of carriers used by the u-th user, k represents the order in which the received signal for the u-th user among the plurality of received signals included in the frame is located k = 0, 1, .. , N u -1, where N represents the number of chips constituting one block, Is the selection signal ( ) Results in a delay of N by Is the selection signal ( ) Conjugate. At this time, the selection signal ( ) Is determined as a received signal for the u-th user expressed in Equation 3 in the initial state.
    [29]
    [30] Where r k [u] represents the received signal for the u-th user, n k [u] represents the noise component included in the received signal r k [u] , and z k (i) [u] represents Received signal (r k [u] ) for the u -th user represents the degree to which the received signals for the i (1≤i≤U-1) -th user interference.
    [31] After the tenth step, the amount of interference representing the degree to which the received signals for the i-th user interfered with the received signal (r k [u] ) for the i-th user is estimated (step 12). Here, the degree to which the i th other user, one of the other users, interferes with the u th user (multiple access interference) ( ) Is estimated as in Equation 4 below.
    [32]
    [33] here, Denotes an estimate of the degree of interference z k (i) [u] , Δ iu denotes n i -n u , n i denotes the frequency offset given to the i th user, and n u denotes the u th user Denotes the frequency offset given to, L u denotes the number of times the user symbol is repeated at the transmitter for the u th user, L i denotes the number of times the user symbol is repeated at the transmitter for the i th user, Denotes the frequency offset for the i th user, q i is a i denotes an initial phase offset of the second block, k% N i denotes the remainder when A is divided to k by N i, N i is the i-th user is using Indicates the number of carriers to be. At this time, the frequency offsets n i and n u are offsets different from the frequency offset compensated by the present invention.
    [34] Accordingly, the degree to which the received signals interfere with the received signal for the u th user except for the u th user among the received signals for the U users ( The sum represented by Equation 5 below may be determined as the interference amount.
    [35]
    [36] After the twelfth step, the amount of interference is subtracted from the received signal r k [u] as shown in Equation 6 below, and the subtracted result is a feedback signal that can be a selection signal in a steady state as described above. (Step 14).
    [37]
    [38] After the fourteenth step, it is determined whether the tenth, twelfth and fourteenth steps have been repeatedly performed a predetermined number of times (step 16). Here, the predetermined number of times is determined in proportion to the reduction rate of the received signal-to-noise ratio (SNR). That is, as the received signal-to-noise ratio decreases, the predetermined number of times can be set larger.
    [39] If it is determined that the tenth, twelfth and fourteenth steps have not been performed a predetermined number of times, the process proceeds to the tenth step and the tenth to the fourteenth steps are repeatedly performed. Here, in the frequency offset compensation method according to the present invention, when the tenth step is first performed, the selection signal is determined as the received signal, but when the tenth step is repeatedly performed, the selection signal is determined as the feedback signal, not the received signal. do. However, if it is determined that the tenth, twelfth and fourteenth steps have been repeatedly performed a predetermined number of times, the feedback signal finally determined in the fourteenth step ( ) And the frequency offset finally estimated in the tenth step ( ), You can use the ) Is estimated by the following Equation 7, and the estimated transmission signal ( ) (Step 18).
    [40]
    [41] Where q u represents the initial phase offset of the u-th block, Represents an estimate of q u .
    [42] On the other hand, with reference to the accompanying drawings the configuration and operation of the IFDMA communication apparatus having a frequency offset compensation apparatus according to the present invention for performing the frequency offset compensation method for interleaved frequency division multiple access according to the present invention as follows. Explain.
    [43] 2 is a block diagram of an IFDMA communication device having a frequency offset compensation device according to the present invention, wherein the first, ..., u, ..., and Uth transmitters for first to Uth users 30 are shown. , ..., 32, ..., and 34), first, ..., u, ..., and U-th channels (40, ..., 42, ..., and 44), synthesizer ( 46), the first, ..., u, ..., and U-th receivers (50, ..., 52, ..., and 54) for the first through U-th users.
    [44] The first transmitter 30 shown in FIG. 2 is composed of an L 1 repeater 60, a multiplier 62, a first Cyclic Prefix (CP) insert 64 and a multiplier 66, The u th transmitter 32 is composed of an L u repeater 70, a multiplier 72, a u th cyclic prefix insert 74 and a multiplier 76, and the U th transmitter 34 comprises an L U repeater. 80, a multiplier 82, a U-circulation prefix inserting portion 84, and a multiplier 86.
    [45] Here, the L 1 repeater 60 repeats the user symbol [a k (1) ] for the first user L 1 times and outputs the result to the multiplier 62, and the L u repeater 70 transmits to the u th user. The user symbol [a k (u) ] is repeated L u times and output to the multiplier 72, and the L U repeater 80 outputs the user symbol [a k (U) ] for the U th user L U times. Repeatedly serves to output to the multiplier 82. Here, the user symbol [a k (1) ] is composed of N 1 quadrature amplitude modulation (QAM) encoded signals, and the user symbol [a k (u) ] is N u quadrature amplitude modulation. And a user symbol [a k (U) ] consists of N U quadrature amplitude modulated (QAM) encoded signals.
    [46] At this time, the multipliers 62, 72, and 82 output the repeated results output from the L 1 , L u, and L U iterations 60, 70, and 80, respectively. , And And multiply by and output the multiplied results to the first, u, and U th CP insertion units 64, 74, and 84, respectively.
    [47] The first, u, or U th CP inserts 64, 74, or 84, which serve to remove interblock interference, insert a cyclic prefix CP before the result multiplied by the multiplier 62, 72, or 82. Then, the inserted result is output to the multipliers 66, 76 or 86, respectively.
    [48] In order to convert the result of inserting the cyclic prefix (CP) into a radio frequency (RF) signal, the multipliers 66, 76 and 86 are first, u and U th CP inserts 64, 74. Results of inserting the cyclic prefix CP respectively outputted from Multiply by and output the multiplied results to the first, ..., u, ..., and U-th channels 40, ..., 42, ..., and 44, respectively.
    [49] At this time, the transmission signals passing through the first, ... u, ... and U- th channels 40, ..., 42, ... and 44 [y k (1) , ... , y k (u) , ... and y k (U) ] are synthesized and the synthesized result is added with noise in synthesizer 46. Here, synthesizer 46 is shown to conceptually illustrate that noise is included in the synthesized result as a device that does not actually exist.
    [50] The first receiver 50 illustrated in FIG. 2 includes a multiplier 90, a first CP remover 92, a multiplier 94, a first overlap / add unit 96, and a frequency offset compensator. 98 and the first equalization and inspection unit 100. Similarly, u-th receiver 52 includes multiplier 110, u-CP remover 112, multiplier 114, u-overlap / adder 116, frequency offset compensation device 118 and u-equalization. And an inspection unit 120. In addition, the U-th receiver 54 includes a multiplier 130, a U-CP remover 132, a multiplier 134, a U-overlap / adder 136, a frequency offset compensator 138, and a U-equalization and It consists of an inspection unit 140.
    [51] In order to convert the radio frequency signal, which is a synthesized result, to a baseband signal, the multipliers 90, 110, and 130 are synthesized by the synthesizer 46. Multiply by and output the multiplied result to the first, u, and U th CP removing units 92, 112, or 132, respectively. Here, the frequency generated by the transmission oscillator ( ) And the frequency generated by the receiving oscillator ( ) Corresponds to the frequency offset compensated by the present invention.
    [52] At this time, the first, u, or U-th CP removing unit 92, 112, or 132 removes the cyclic prefix CP from the result of multiplication in the multiplier 90, 110, or 130, and the cyclic prefix CP ) Is output to the multiplier (94, 114 or 134). Multipliers 94, 114, and 134 determine the results of removing the cyclic prefix CP output from the first, u, and Uth CP removers 92, 112, and 132. , And And multiply by and output the multiplied results to the first, u, and U th overlap / adders 96, 116, and 136, respectively.
    [53] At this time, the first, u, and U th overlap / adders 96, 116, and 136 output the multiplied result output from the multipliers 94, 114, and 134 for N 1 , N u, and N U periods. After overlapping, it is output to the frequency offset compensation devices 98, 118, and 138, respectively. For example, a received signal r k (u) , such as Equation 3, may be output from the u- th overlap / adder 116 to the frequency offset compensator 118.
    [54] The frequency offset compensation device 98, 118 or 138 shown in FIG. 2 performs the frequency offset compensation method according to the present invention shown in FIG. 1 to transmit a signal [y k (1) , y k (u) or y k. (U) ], and the estimated transmission signal [ , or ] Is output to the first, u, or Uth equalization and inspection unit (100, 120, or 130), respectively.
    [55] The first, u, and u th equalization and inspection units 100, 120, and 130 are output from the frequency offset compensators 98, 118, and 138, and are generated from inter-symbol interference due to the influence of a channel. Estimated transmission signals with , And Equalize] to remove the ISI and estimate the user symbols [a k (1) , a k (u) and a k (U) ], respectively, and estimate the estimated user symbols [ , And ]
    [56] Hereinafter, with reference to the accompanying drawings, the configuration and operation of the frequency offset compensation device 118 for interleaved frequency division multiple access according to the present invention for performing the above-described frequency offset compensation method for interleaved frequency division multiple access Explain as follows. At this time, each of the frequency offset compensation devices 98 and 138 shown in FIG. 2 has the same configuration as the frequency offset compensation device 118 and performs the same operation.
    [57] 3 is a block diagram of a frequency offset compensator according to the present invention, which includes a main frequency offset estimator 160, an interference amount estimator 162, a subtractor 164, a transmission signal estimator 166, and a controller. It consists of 168.
    [58] In order to perform the tenth step illustrated in FIG. 1, the main frequency offset estimator 160 illustrated in FIG. 3 receives the received signal r k [ in response to the first control signal C1 input from the controller 168. u] ) or feedback signal ( ) Is determined as the selection signal, and the frequency offset (i) for the u-th user from the selection signal ) Is estimated as in Equation 1 above, and the estimated frequency offset ( ) Are output to the interference amount estimator 162 and the transmission signal estimator 166, respectively. To this end, the controller 168 generates a first control signal C1 in response to a result of analyzing the state of the frequency offset compensator shown in FIG. 3, and adds the generated first control signal C1 to the main frequency offset. Output to the government 160. For example, the controller 168 determines the reception signal r k [u] as the selection signal when the frequency offset compensator shown in FIG. 3 is in the initial state described above, and when the frequency offset compensator is in the normal state described above. Feedback signal ( ) Is generated and output to the main frequency offset estimator 160 to determine.
    [59] FIG. 4 is a block diagram of a preferred embodiment 160A of the main frequency offset estimator 160 shown in FIG. 3 according to the present invention, and includes a first selector 180, a first delay unit 182, and a first delay unit 182. It consists of one conjugate calculation part 184, the 1st multiplication part 186, and the 1st offset calculation part 188. As shown in FIG.
    [60] The first selector 180 of the main frequency offset estimator 160A shown in FIG. 4 receives the feedback signal inputted from the subtractor 164. ) And one of the received signals r k [u] input from the outside are selected in response to the first control signal C1 input from the controller 168, and the selected result is selected as the first delay unit 182. ) And the first conjugate calculation unit 184, respectively, and output through the output terminal OUT2. For example, when the state of the frequency offset compensator shown in FIG. 3 is in an initial state through the first control signal C1 input from the controller 168, the first selector 180 receives an externally received signal r. k [u] ) is determined and output as a selection signal, and the first selection unit 180 subtracts the subtraction unit 164 when the frequency offset compensator shown in FIG. 3 is in a normal state through the first control signal C1. Feedback signal input from ) Is determined as a selection signal and output.
    [61] The first delay unit 182 delays the selection signal input from the first selection unit 180 by the unit block N, and outputs the delayed selection signal to the first multiplier 186. At this time, the first conjugate calculation unit 184 calculates the conjugate of the selection signal input from the first selection unit 180 and outputs the calculated conjugate of the selection signal to the first multiplication unit 186.
    [62] The first multiplier 186 multiplies the conjugate of the selection signal input from the first conjugate calculator 184 and the delayed selection signal input from the first delay unit 182, and multiplies the multiplied result by the first offset calculator. Output to (188).
    [63] The first offset calculator 188 accumulates the multiplied result input from the first multiplier 186 by one less than the number of carriers (N u ) used by the u th user (N u −1), and accumulates the accumulated result. The angle ∠C u is obtained, and the angle ∠C u is divided by a predetermined number, for example, 1 / 2π, as shown in Equation 1 above, and the divided result is estimated by an estimated frequency offset ( Output as
    [64] The first selector 180, the first delay unit 182, the first conjugate calculator 184, the first multiplier 186, and the first offset calculator 188 illustrated in FIG. 4 are the controller 168. It is enabled in response to the second control signal C2 output from). At this time, to perform the sixteenth step illustrated in FIG. 1, the controller 168 checks whether a predetermined period has elapsed and outputs a second control signal C2 in response to the result of the inspection. Here, elapse of a predetermined period means that the tenth to fourteenth steps have been repeatedly performed a predetermined number of times. As a result, when it is recognized through the second control signal C2 that the predetermined period has not elapsed, the first selector 180, the first delay unit 182, the first conjugate calculator 184, and the first multiplier 186 and the first offset calculator 188 are enabled.
    [65] In order to perform the twelfth step, the interference amount estimator 162 receives the received signals r k [1] , ..., r k [u-1] , r k [u + 1 for the i th other users. ] , ..., and r k [U] ) receive signals for other users with the amount of interference, such as Equation 5, above, which indicates the degree to which the received signal r k [u] for the u th user has interfered. (r k [1] , ..., r k [u-1] , r k [u + 1] , ... and r k [U] ), the first selector 180 shown in FIG. Signal and estimated frequency offset output from ), And outputs the estimated interference amount to the subtraction unit 164.
    [66] In order to perform the fourteenth step, the subtraction unit 164 subtracts the estimated interference amount from the received signal r k [u] as shown in Equation 6, and subtracts the subtracted result from the feedback signal ( ) Are output to the main frequency offset estimator 160 and the transmission signal estimator 166, respectively.
    [67] In order to perform the eighteenth step, the transmission signal estimator 166 responds to the second control signal C2 generated from the controller 168 and finally receives the feedback signal (the input signal) from the subtractor 164. ) And an estimated frequency offset input from the main frequency offset estimator 160 ) Is estimated as shown in Equation 7 above, and the estimated transmission signal ) Is output through the output terminal OUT1. For example, when it is recognized that the predetermined period has passed through the second control signal C2, the transmission signal estimator 166 transmits the transmission signal ( Perform an operation of estimating. In this case, the above-described interference amount estimator 162 and the subtractor 164 also operate in response to the second control signal C2 generated from the controller 168. That is, when it is recognized that the predetermined period has passed through the second control signal C2, the interference amount estimating unit 162 and the subtracting unit 164 are enabled.
    [68] Hereinafter, the configuration and operation of each of the preferred embodiments of the present invention of the interference amount estimator 162 and the transmission signal estimator 166 shown in FIG. 3 will be described with reference to the accompanying drawings.
    [69] FIG. 5 is a block diagram of a preferred embodiment 166A of the transmission signal estimator 166 shown in FIG. 3 according to the present invention. The first gain calculator 190, the inverter 192, and the second multiplication are shown in FIG. Section 194.
    [70] The first gain calculator 190 of the transmission signal estimator 166A shown in FIG. 5 uses the estimated frequency offset input from the main frequency offset estimator 160. ), The gain as shown in Equation 8 is calculated, and the calculated result is output to the inverting unit 192 as the first gain.
    [71]
    [72] At this time, the inverting unit 192 inverts the first gain input from the first gain calculating unit 190 and outputs the inverted result to the second multiplication unit 194. The second multiplier 194 may include the first gain inverted by the inverting unit 192 and a feedback signal finally input from the subtracting unit 164. ) And multiply the result by the estimated transmission signal ( Output as
    [73] The first gain calculator 190, the inverter 192, and the second multiplier 194 shown in FIG. 5 are enabled in response to the second control signal C2 input from the controller 168. For example, when it is recognized that a predetermined period has passed through the second control signal C2, the first gain calculator 190, the inverter 192, and the second multiplier 194 are enabled.
    [74] FIG. 6 is a block diagram of a preferred embodiment 162A according to the present invention of the interference estimator 162 shown in FIG. 3, and includes the first, ..., i, ..., and U-1 species. (sub) frequency offset estimators 200, ..., 202, ..., and 204, first, ..., i, ..., and U-1 degree estimation units 210, ... , 212,... And 214, a synthesizer 216, and a feedback signal generator 218.
    [75] I type frequency, which is one of the first, ..., i, ..., and U-1 type frequency offset estimation units 200, ..., 202, ..., and 204 shown in FIG. The offset estimator 202 receives the feedback signal z k (i) [i] for the i th other user or the i th other user in response to the first control signal C1 input from the controller 168. Select the signal r k [i] , estimate the frequency offset for the i-th other user from the selected result, and estimate the estimated frequency offset ( ) Is output to the i th degree estimator 212. At this time, the frequency offset is obtained as in Equations 1 and 2 described above. In this case, u may be replaced with i in Equations 1 and 2.
    [76] For example, the first type frequency offset estimator 200 responds to the first control signal C1 input from the controller 168 and returns a feedback signal z k (1) [1] or the first signal for the first other user. Select the received signal r k [1] for the first other user, estimate the frequency offset for the first other user from the selected result, and ) Is output to the first degree estimator 210. Similarly, the U-1 type frequency offset estimator 204 responds to the first control signal C1 input from the controller 168 and returns a feedback signal z k (U-1) for the U-1 th user. [U-1] ) or the received signal r k [U-1] for the U-1 th other user, estimate a frequency offset for the U-1 th other user from the selected result, and estimate the estimated frequency offset( ) Is output to the U-1th degree estimator 214.
    [77] FIG. 7 is a block diagram of a preferred embodiment 202A of the i-th type frequency offset estimator 202 of FIG. 6 according to the present invention, and includes a second selector 230 and a second delay unit 232. , A second conjugate calculation unit 234, a third multiplication unit 236, and a second offset calculation unit 238.
    [78] The second selector 230 shown in FIG. 7 receives the feedback signal z k (i) [i] for the i-th other user or the received signal r k [i] for the i-th other user input from the outside. ) Is selected in response to the first control signal C1, and the selected result is output to the second delay unit 232 and the second conjugate calculation unit 234, respectively, and the i th degree is added through the output terminal OUT5. It also outputs to the government 212. For example, when the frequency offset compensating device is recognized as the initial state through the first control signal C1, the second selector 230 selects the reception signal r k [i] for the i-th other user. However, when the frequency offset compensator is recognized as being normal through the first control signal C1, the second selector 230 receives the feedback signal z k (i) [i] for the i-th other user. Choose.
    [79] The second delay unit 232 delays the selected result input from the second selector 230 by the unit block N, and outputs the delayed result to the third multiplier 236. The second conjugate calculator 234 calculates the conjugate of the selected result input from the second selector 230, and outputs the calculated result to the third multiplier 236. The third multiplier 236 multiplies the calculated result input from the second conjugate calculator 234 and the delayed result input from the second delay unit 232, and multiplies the multiplied result by the second offset calculator 238. )
    [80] The second offset calculator 238 accumulates the multiplied result input from the third multiplier 236 by one less than the number of carriers (N i ) used by the i-th other user (N i −1), seeking the angle (∠C i) of the accumulated result, and the predetermined angle (∠C i) for example divided by 1 / 2π, the frequency offset estimate for the division result to the i th other users ( Output as
    [81] Meanwhile, the first, ..., i, ..., and U-1 degree estimators 210, ..., 212, ..., and 214 shown in FIG. Estimate the first, ..., i, ... and U-1 (interfering) degrees, respectively, and estimate the estimated first, ..., i, ..., and U-1 degrees ( , ..., , ... and ) Are output to the combiner 216 and the feedback signal generator 218, respectively. For example, the i-th degree estimator 212, which is one of the first, ..., i-th, ..., and U-1th degree estimators 210, ..., 212, ..., and 214, The i th degree corresponding to the degree to which the received signal r k [u] for the u th user interferes with the received signal r k [i] for the i th other user ( ) Is the frequency offset for the ith other user ( And the result selected by the i-type frequency offset estimator 202, for example, the output selected through the output terminal OUT5 from the second selector 230 of the i-type frequency offset estimator 202A shown in FIG. Estimate the result, and the estimated result ( ) Is output to the combiner 216 and the feedback signal generator 218. Similarly, the first degree estimator 210 corresponds to a degree of interference between the received signal r k [u] for the u th user and the received signal r k [1] for the first other user. 1 degree ( ) Is the frequency offset for the first other user ( ) Is estimated from the result selected by the first type frequency offset estimator 200 and the estimated result ( ) Is output to the combiner 216 and the feedback signal generator 218. In addition, the U-th degree estimator 214 interferes with the received signal r k [u] for the u-th user by the received signal r k [U-1] for the U-th other user. U-1 degree corresponding to degree ( ) Is the U-1 frequency offset for the other user ( ) And the result selected by the U-1 type frequency offset estimator 204, and the estimated result ( ) Is output to the combiner 216 and the feedback signal generator 218.
    [82] FIG. 8 is a block diagram of a preferred embodiment 212A according to the present invention of the ith degree estimator 212 shown in FIG. 6, which includes a comparator 250, a signal expander and reducer 252, and a second The gain calculator 254, the third gain calculator 256, the fourth and fifth multipliers 258 and 260, and the third selector 262 are configured.
    [83] The comparator 250 compares the number of subcarriers (N i ) used by the i-th other user with the number (N u ) of subcarriers used by the u-th user, and compares the result of the comparison with the third selector 262. ) And the signal extension and contraction unit 252, respectively. At this time, the signal extension and contraction unit 252 expands or contracts the length of the selected result input from the second selector 230 through the input terminal IN3 in response to the compared result input from the comparator 250. . If, for example, through the comparison result input from the comparison unit (250) i th other user and the number of sub-carriers to use the number of sub-carriers to (N i) is used by the u th user (N u) recognized as being less, The signal expansion and contraction unit 252 selects the selected result inputted from the second selection unit 230. ) Is extended as shown in Equation 9 below, and the result of the extension is output to the fourth multiplier 258.
    [84]
    [85] However, if the i th other user and the number (N i) of sub-carriers used by a recognized to be greater than the sub-carrier number (N u) of which the u th user using through the comparison result input from the comparison unit 250 , The signal expanding and contracting unit 252 selects the selected result inputted from the second selector 230. ) Is reduced as shown in Equation 10, and the reduced result is output to the fifth multiplier 260.
    [86]
    [87] The second gain calculator 254 may calculate a frequency offset (i) for the i th other user input from the i th type frequency offset estimator 202. ) Is calculated as in Equation 11, and the calculated result is output to the fourth multiplier 258 as a second gain.
    [88]
    [89] The third gain calculator 260 may calculate a frequency offset (i) for the i-th other user input from the i-th type frequency offset estimator 202. ), The gain is calculated as in Equation 12, and the calculated result is output to the fifth multiplier 260 as a third gain.
    [90]
    [91] The fourth multiplier 258 inputs the signal expanding and contracting unit 252. The multiplied result is multiplied by the second gain input from the second gain calculator 254 and the multiplied result is output to the third selector 262. The fifth multiplier 260 inputs from the signal extending and contracting unit 252. The multiplied result is multiplied by the third gain input from the third gain calculator 256 and the multiplied result is output to the third selector 262.
    [92] The third selector 262 selects one of the multiplied results input from the fourth and fifth multipliers 258 and 260 in response to the compared result input from the comparator 250, and selects the selected result. I degree ( Output as If, for example, through the result compared by the comparison unit (250) i th other user and the number (N i) of sub-carriers used by the recognition on a number (N u) or less of sub-carriers for the u th user using the third The selector 262 selects a result multiplied by the fourth multiplier 258. However, if the i th other user and the number (N i) of sub-carriers used by a recognized to be greater than the sub-carrier number (N u) of which the u th user using through the result compared by the comparison unit 250, the The third selector 262 selects a result multiplied by the fifth multiplier 260.
    [93] Meanwhile, the synthesis unit 216 shown in FIG. 6 is configured from the first, ..., i, ..., and U-1 degree estimators 210, ..., 212, ..., and 214. The first, ..., i, ..., and U-1 degrees to be output are synthesized, and the synthesized result is output through the output terminal OUT4 as an interference amount expressed as in Equation 5 described above.
    [94] The feedback signal generator 218 shown in FIG. 6 includes the first gain input through the input terminal IN1 and the selection signal input through the input terminal IN2, and the first, ..., i, ..., U Received to the first, ..., i, ... and U-1 degrees and other users input from the -1 degree estimators 210, ..., 212, ..., and 214 From the signals r k [1] , ..., r k [i] , ... and r k [U-1] , the first, ..., i, ... and U-1 Feedback signals used in the longitudinal frequency offset estimation units 200, ..., 202, ..., and 204 (z k (1) [1] , ..., z k (i) [i],. And z k (U-1) [U-1] ).
    [95] FIG. 9 is a block diagram of a preferred embodiment 218A according to the present invention of the feedback signal generation unit 218 shown in FIG. 6, and includes first, ..., i, ..., and U-1. Subtractors 280,..., 282,..., And 284 and a sixth multiplier 286.
    [96] According to an embodiment of the present invention, the feedback signal generator 218A shown in FIG. 9 includes a sixth multiplier 286 so that the first gain calculator of the transmission signal estimator 166A shown in FIG. The first gain output from the output terminal OUT3 from the input terminal 190 is input through the input terminal IN4, and the selection signal output from the first selection unit 180 of the main frequency offset estimator 160A through the output terminal OUT2 is output. Input through the input terminal IN5, multiply the input first gain and the selection signal, and multiply the result by the first, ..., i, ... and U-1 subtractors 280, ... , 282, ..., and 284, respectively.
    [97] According to another embodiment of the present invention, the feedback signal generator 218A shown in FIG. 9 may further include a gain generator (not shown). In this case, the gain generator estimates the estimated frequency offset inputted from the main frequency offset estimator 160 through the input terminal IN1. ) Can be calculated as shown in Equation 8 above. At this time, instead of inputting the first gain from the transmission signal estimator 166A through the input terminal IN4, the sixth multiplier 286 inputs the first gain generated by the gain generator and inputs the first gain. Is multiplied by the selection signal input via input terminal IN5.
    [98] The first subtractor 280 subtracts the first degree among the first to U-1 degrees from the received signal r k [1] for the first other user ( , ..., , , ..., And ) Is subtracted from the result of multiplication by the sixth multiplier 286 and the subtracted result is used by the first type frequency offset estimator 200. ) Is output through the output terminal OUT6.
    [99] The first subtractor 282, which is one of the first, ..., i, ..., and U-1 subtractors 280, ..., 282, ..., and 284, is the i-th other user. Degrees excluding the i th degree among the first through U-1 degrees from the received signal r k [i] for ( , , ..., , ..., And ) Is subtracted from the result multiplied by the sixth multiplier 286, and the feedback signal (used by the i-type frequency offset estimator 202) is subtracted. ) Is output through the output terminal OUT7.
    [100] The U-1 subtractor 284 subtracts the U-1 degree among the first through U-1 degrees from the received signal r k [U-1] for the U-1 th other user ( , , ..., , , ... and ) And a feedback signal used by the U-1 type frequency offset estimator 204 to subtract the result multiplied by the sixth multiplier 286. ) Is output through the output terminal OUT8.
    [101] Hereinafter, to facilitate understanding of the method and apparatus for compensating the frequency offset for interleaved frequency division multiple access according to the present invention described above, it is assumed that U = 8 and each user uses 32 subcarriers. In addition, each subcarrier uses Quadrature Phase Shift Keying (QPSK) and assumes that all users have the same frequency offset and the channel is Additive White Gaussian Noise (AWGN).
    [102] FIG. 10 is a diagram illustrating a constellation of an ideal received signal having no frequency offset, in which the vertical axis represents quadrature (Q) and the horizontal axis represents in phase (I: In phase).
    [103] Referring to FIG. 10, each of the points [(-1, -1), (1, -1), (-1, 1) and (1,1)] representing the received signal on the coordinates of I and Q is circular. Floating form. This is due to the influence of noise coming through the channel.
    [104] FIG. 11 is a diagram illustrating a property of a received signal when the frequency offset is 3% of the interval between subcarriers.
    [105] FIG. 12 is a diagram illustrating a constellation of a received signal that can be seen when applying the frequency offset compensation method and apparatus according to the present invention to the constellation shown in FIG. 11.
    [106] Referring to FIG. 11, the constellation is displayed in a circle due to the influence of the frequency offset and the interference between users. When the frequency offset compensation method and apparatus according to the present invention are applied to the circular constellation, the degree of spreading around the point only slightly increases compared to the constellation shown in FIG. 10, and the circular as shown in FIG. 12 is removed. It can be seen that.
    [107] In addition, the relationship between the predetermined number of times, the received signal-to-noise ratio (SNR) and the bit error rate (BER) will be described as follows.
    [108] 13 is a graph showing the change of the SNR according to the frequency offset, where the horizontal axis represents the frequency offset and the vertical axis represents the SNR, respectively.
    [109] 14 is a graph showing a change in BER according to a frequency offset, in which the horizontal axis represents frequency offset and the vertical axis represents BER, respectively.
    [110] 13 and 14, 'No Op' represents the SNR when the frequency offset is not compensated for, and 'Iter 0' represents the SNR when the 10th to 14th steps are not repeatedly performed, and 'Iter 1' 'Represents the SNR when the predetermined number = 1,' Iter 2 'represents the SNR when the predetermined number = 2,' Iter 3 'represents the SNR when the predetermined number = 3, and' Iter 4 ' SNR when the predetermined number = 4, and 'Iter 5' indicates the SNR when the predetermined number = 5.
    [111] As can be seen from FIG. 13, it can be seen that the SNR is rapidly improved as the predetermined number is increased. In particular, when comparing 'No Op' and 'Iter 1', it can be seen that when the frequency offset is 10% of the interval between subcarriers, the SNR is improved by about 12 dB when the frequency offset is compensated. Therefore, when the frequency offset is large, increasing the predetermined number of times may improve the SNR. As can be seen from FIG. 14, as the frequency offset increases, a predetermined number of times must be increased to obtain a BER of about 10 −6 .
    [112] As described above, a method and apparatus for compensating frequency offset for interleaved frequency division multiple access according to the present invention is present instead of removing the frequency offset unlike the conventional method using an analog RF / IF stage for removing the frequency offset. Baseband elimination, as well as distortions in the amplitude and phase of the received signal due to frequency offset, can be eliminated at baseband, reducing circuit design and implementation costs, and compensating for frequency offset before estimating channel characteristics. Has the effect.
    权利要求:
    Claims (13)
    [1" claim-type="Currently amended] In an interleaved frequency division multiple access (IFDMA), a frequency offset compensation method for compensating a frequency offset between a transmission signal and a reception signal for u th (1 ≦ u ≦ U), where U represents the number of users. In
    (a) estimating the frequency offset from a selection signal determined by the received signal in an initial state and a feedback signal in a steady state;
    (b) estimating an amount of interference representing a degree to which the received signals for the i-th user are interfered with the received signal for the u-th user;
    (c) subtracting the estimated interference amount from the received signal and determining the subtracted result as the feedback signal;
    (d) determining whether the steps (a), (b) and (c) have been repeatedly performed a predetermined number of times, and the steps (a), (b) and (c) are performed a predetermined number of times. If it is determined that it has not been performed repeatedly, proceeding to the step (a); And
    (e) if it is determined that the steps (a), (b) and (c) have been repeatedly performed the predetermined number of times, using the feedback signal and the estimated frequency offset finally determined in step (c) Estimating the transmission signal.
    [2" claim-type="Currently amended] The method of claim 1, wherein step (a)
    Estimating the frequency offset from the selection signal as follows and proceeding to step (b).

    (here, Represents the frequency offset, Where C u represents the correlation ego, Denotes the selection signal, N u denotes the number of carriers used by the u-th user, k denotes the sequence number of the received signal for the u-th user among a plurality of received signals included in the frame, k = 0, 1, ..., N u -1, N represents the number of chips forming a block, Is the selection signal ( ) Results in a delay of N by Is the selection signal ( Represents a conjugate.)
    [3" claim-type="Currently amended] The method of claim 2, wherein step (b)
    After the step (a), the degree of the i-th user among the other users interfered with the u-th user ( ) Is estimated as follows, and proceeds to step (c).

    (Where, k% N i denotes the remainder when A is divided to k by N i, N i denotes the number of carriers used by the i th user, L i is the user symbols in a transmitter for the i th user L u represents the number of times the user symbol is repeated in the transmitter for the u-th user, Δ iu represents n i -n u , and n i represents the frequency offset given to the i-th user. N u represents the frequency offset given to the u th user, q i represents the initial phase offset of the i th block, to be.)
    [4" claim-type="Currently amended] The method of claim 3, wherein step (c)
    After the step (b), the estimated interference amount from the received signal ( ) Is subtracted as follows, and the subtracted result is the feedback signal ( C), and proceed to step (d).

    (here, Represents the received signal.)
    [5" claim-type="Currently amended] 5. The method of claim 4, wherein the predetermined number of times is determined in proportion to a reduction of the received signal-to-noise ratio.
    [6" claim-type="Currently amended] The method of claim 5, wherein step (e)
    If it is determined that the steps (a), (b) and (c) have been repeatedly performed the predetermined number of times, the feedback signal finally determined in step (c) ( ) And the estimated frequency offset ( Using the transmit signal ( ) Is estimated as follows.

    (here, Denotes the estimated transmission signal and q u denotes the initial phase offset of the u-th block.)
    [7" claim-type="Currently amended] In an interleaved frequency division multiple access (IFDMA), a frequency offset compensation device that compensates for a frequency offset between a transmission signal and a reception signal for u th (1 ≦ u ≦ U), where U represents the number of users. In
    A main frequency offset estimator for determining the received signal or feedback signal as a selection signal in response to a first control signal, estimating the frequency offset from the selection signal, and outputting the estimated frequency offset;
    The received signals for the other users, the selection signal, and the amount of interference representing the degree to which the received signals for the i (1 ≦ i ≦ U-1) th other users interfere with the received signal for the u th user. And an interference amount estimator which estimates from the estimated frequency offset and outputs the estimated interference amount.
    A subtraction unit which subtracts the estimated interference amount from the received signal and outputs the subtracted result as the feedback signal;
    A controller configured to generate the first control signal in response to a result of analyzing the state of the frequency offset offset compensator, check whether a predetermined period has elapsed, and output a second control signal in response to the checked result; And
    A transmission signal estimator for estimating the transmission signal from the feedback signal and the estimated frequency offset finally inputted from the subtraction section in response to the second control signal, and outputting the estimated transmission signal,
    And the main frequency offset estimator, the interference amount estimator, and the subtractor in response to the second control signal.
    [8" claim-type="Currently amended] The method of claim 7, wherein the main frequency offset estimator
    A first selector configured to select one of the feedback signal input from the subtractor and the received signal input from the outside in response to the first control signal, and output a selected result as the select signal;
    A first delay unit delaying the selection signal input from the first selection unit by a unit block and outputting the delayed selection signal;
    A first conjugate calculation unit calculating a conjugate of the selection signal input from the first selection unit and outputting a calculated conjugate of the selection signal;
    A first multiplier configured to multiply the conjugate of the selection signal input from the first conjugate calculation unit with the delayed selection signal input from the first delay unit and output a multiplied result; And
    Accumulating the multiplied result input from the first multiplier by one less than the number of carriers (N u ) used by the u th user (N u −1), obtaining an angle of the accumulated result, and obtaining the angle A first offset calculator which divides by a predetermined number and outputs the divided result as the estimated frequency offset,
    And the first selector, the first delayer, the first conjugate calculator, the first multiplier, and the first offset calculator are enabled in response to the second control signal. Offset compensation device.
    [9" claim-type="Currently amended] The method of claim 8, wherein the transmission signal estimator
    A first gain calculator for calculating the following gain from the estimated frequency offset input from the main frequency offset estimator and outputting the calculated result as a first gain;

    (Where k denotes the order of the corresponding received signal among the received signals included in the frame and k = 0, 1, ..., N u -1, N denotes the number of chips forming one block, L u represents the number of times the user symbol is repeated at the transmitter for the u th user, Denotes a frequency offset for the u th user, Δ iu denotes n i -n u , n i denotes a frequency offset given to the i th user, and n u denotes a frequency offset given to the u th user , q u represents the initial phase offset of the u-th block.)
    An inversion unit inverting the first gain; And
    And a second multiplier for multiplying the inverted first gain and the feedback signal finally inputted from the subtractor and outputting the multiplied result as the estimated transmission signal.
    And the first gain calculator, the inverter, and the second multiplier are enabled in response to the second control signal.
    [10" claim-type="Currently amended] The method of claim 9, wherein the interference amount estimating unit
    First to U-1 sub frequency offset estimators;
    First to U-1 degree estimators for estimating the first to U-1 degrees;
    Synthesis unit; And
    A feedback signal generator,
    The i-th type frequency offset estimator selects a feedback signal for the i-th other user or the received signal for the i-th other user in response to the first control signal, and selects the i-th other user from the selected result. Estimate the frequency offset,
    The i th degree estimating unit offsets the i th degree corresponding to the degree to which the received signal for the u th user interferes with the received signal for the i th other user, the frequency offset for the i th other user. And estimated from the result selected by the i-type frequency offset estimator,
    The synthesis unit synthesizes the first to U-th degrees, and outputs the synthesized result as the interference amount,
    The feedback signal generator is used by the first to U-1 type frequency offset estimators from the first gain and the selection signal, the first to U-1 degrees, and the received signals to the other users. Generating said feedback signals.
    [11" claim-type="Currently amended] 12. The apparatus of claim 10, wherein the i-th type frequency offset estimator
    A second selector configured to select one of the feedback signal for the i-th other user or a received signal for the i-th other user input from the outside in response to the first control signal, and output the selected result;
    A second delay unit delaying the selected result input from the second selector by the unit block and outputting the delayed result;
    A second conjugate calculation unit calculating a conjugate of the selected result input from the second selecting unit and outputting the calculated result;
    A third multiplier for multiplying the calculated result input from the second conjugate calculation unit with the delayed result input from the second delay unit and outputting the multiplied result; And
    Accumulating the multiplied result input from the third multiplier by one less than the number of carriers (N i ) used by the i th other user (N i −1), obtaining an angle of the accumulated result, and And a second offset calculator for dividing an angle by the predetermined number and outputting the divided result as the estimated frequency offset for the i-th other user.
    [12" claim-type="Currently amended] The method of claim 10, wherein the i-th degree estimating unit
    A comparison unit for comparing the i th other user and the number of sub-carriers to use (N i) and the u-th of the number of sub-carriers the user uses (N u) and outputs the comparison result;
    The selected result input from the second selector ( A signal stretching and contracting unit which expands or contracts the length of) in response to the compared result inputted from the comparing unit and outputs the expanded or reduced result as follows;


    (here, Denotes a frequency offset for the i-th user.)
    A second gain calculator configured to calculate a gain from the frequency offset for the i-th other user input from the i-th type frequency offset estimator, and to output the calculated result as a second gain;

    (L i represents the number of times the user symbol is repeated in the transmitter for the i th user, and q i represents the initial phase offset of the i th block.)
    A third gain calculator configured to calculate a gain from the frequency offset for the i-th other user input from the i-th type frequency offset estimator, and to output the calculated result as a third gain;

    (here, to be.)
    A fourth multiplier for multiplying the expanded result and the second gain inputted from the signal expanding and reducing part and outputting the multiplied result;
    A fifth multiplier that multiplies the reduced result input from the signal extending and contracting unit with the third gain and outputs the multiplied result; And
    A third selector configured to select one of the multiplied results input from the fourth and fifth multipliers in response to the compared result input from the comparator, and output the selected result as the i-th degree A frequency offset compensation device for IFDMA, characterized in that.
    [13" claim-type="Currently amended] The method of claim 10, wherein the feedback signal generator
    A sixth multiplier for multiplying the first gain input from the first gain calculator and the selection signal input from the first selector and outputting a multiplied result; And
    Having first through U-1 subtractors,
    And the i-th subtractor subtracts the result of multiplying the sixth multiplier by the excluding the i th degree among the first through U-1 degrees from the received signal for the i th other user. And outputting the subtracted result as the feedback signal used in the i-th type frequency offset estimator.
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    引用文献:
    公开号 | 申请日 | 公开日 | 申请人 | 专利标题
    法律状态:
    2002-07-27|Application filed by 삼성전자주식회사
    2002-07-27|Priority to KR1020020044461A
    2004-02-11|Publication of KR20040011645A
    2008-06-23|Application granted
    2008-06-23|Publication of KR100840608B1
    优先权:
    申请号 | 申请日 | 专利标题
    KR1020020044461A|KR100840608B1|2002-07-27|2002-07-27|Method and apparatus for compensating for the frequency offset in interleaved frequency division multiple access|
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